Power stage with switched mode amplifier and linear amplifier

ABSTRACT

A method for producing an output voltage to a load may include, in a power stage comprising power converter having a power inductor, a plurality of switches arranged to sequentially operate in a plurality of switch configurations, and an output for producing the output voltage comprising a first output terminal and a second output terminal, controlling the linear amplifier to transfer electrical energy from the input source of the power stage to the load in accordance with one or more least significant bits of a digital input signal, and controlling the power converter in accordance with bits of the digital input signal other than the one or more least significant bits to sequentially apply switch configurations from the plurality of switch configurations to selectively activate or deactivate each of the plurality of switches in order to transfer electrical energy from the input source of the power stage to the load.

RELATED APPLICATIONS

This application is a continuation of U.S. Non-Provisional applicationSer. No. 14/840,894 filed on Aug. 31, 2015, which claims priority toU.S. Provisional Patent Application Ser. No. 62/072,059, filed Oct. 29,2014, and U.S. Provisional Patent Application Ser. No. 62/090,142, filedDec. 10, 2014, each of which is incorporated by reference herein in itsentirety.

The present disclosure is related to U.S. application Ser. No.14/612,889 filed Feb. 3, 2015, U.S. application Ser. No. 14/612,946filed Feb. 3, 2015, U.S. application Ser. No. 14/612,734 filed Feb. 3,2015, U.S. application Ser. No. 14/706,587 filed May 7, 2015, U.S.application Ser. No. 14/706,624 filed May 7, 2015, U.S. application Ser.No. 14/706,656 filed May 7, 2015, and U.S. application Ser. No.14/706,680 filed May 7, 2015, each of which is incorporated by referenceherein in its entirety.

FIELD OF DISCLOSURE

The present disclosure relates in general to circuits for audio devices,including without limitation personal audio devices such as wirelesstelephones and media players, and more specifically, to a power stagewith a switch mode amplifier and a linear amplifier mode for driving anaudio transducer of an audio device.

BACKGROUND

Personal audio devices, including wireless telephones, such asmobile/cellular telephones, cordless telephones, mp3 players, and otherconsumer audio devices, are in widespread use. Such personal audiodevices may include circuitry for driving a pair of headphones or one ormore speakers. Such circuitry often includes a speaker driver includinga power amplifier for driving an audio output signal to headphones orspeakers.

One existing approach to driving an audio output signal is to employ aspeaker driver, such as speaker driver 100 depicted in FIG. 1. Speakerdriver 100 may include an envelope-tracking boost converter 102 (e.g., aClass H amplifier) followed by a full-bridge output stage 104 (e.g., aClass D amplifier) which effectively operates as another converterstage. Boost converter 102 may include a power inductor 104, switches106, 108, and a capacitor 110 arranged as shown. Full-bridge outputstage 104 may include switches 112, 114, 116, and 118, inductors 120 and124, and capacitors 122 and 126 as shown.

Speaker drivers such as speaker driver 100 suffer from numerousdisadvantages. One disadvantage is that due to switching in output stage104, such a speaker driver 100 may give rise to large amounts ofradiated electromagnetic radiation, which may cause interference withother electromagnetic signals. Such radiated electromagneticinterference may be mitigated by LC filters formed using inductor 120and capacitor 122 and inductor 124 and capacitor 126. However, such LCfilters are often quite large in size, and coupling capacitors 122 and124 to the terminals of the output transducer may have a negative impacton the power efficiency of speaker driver 100.

In addition, such architectures often do not handle large impulsivesignals. To reduce power consumption, a power supply voltage V_(SUPPLY)may be varied in accordance with the output signal, such that V_(SUPPLY)may operate at lower voltage levels for lower output signal magnitudes.Thus, if a signal quickly increases, adequate time may not be present toincrease voltage V_(SUPPLY), thus leading to signal clipping unless adelay is placed in the signal path. However, adding a delay to a signalpath may cause incompatibility with other types of audio circuits, suchas adaptive noise cancellation circuits.

SUMMARY

In accordance with the teachings of the present disclosure, one or moredisadvantages and problems associated with existing approaches todriving an audio output signal to an audio transducer may be reduced oreliminated.

In accordance with embodiments of the present disclosure, a power stagefor producing an output voltage to a load may include a power converter,a linear amplifier, and a controller. The power converter may include aplurality of switches arranged to sequentially operate in a plurality ofswitch configurations and an output for producing the output voltagecomprising a first output terminal and a second output terminal, whereina first switch of the plurality of switches is coupled to the firstoutput terminal and a second switch of the plurality of switches iscoupled to the second output terminal. The linear amplifier may becoupled to the output. The controller may be configured to: (i) in afirst mode of operation of the power stage, enable the linear amplifierto transfer electrical energy from an input source of the power stage tothe load and disable the plurality of switches from transferringelectrical energy from the input source to the load; and (ii) in asecond mode of operation of the power stage, sequentially enable thelinear amplifier in accordance with a probability which is a function ofthe output voltage to transfer electrical energy from the input sourceof the power stage to the load and sequentially apply switchconfigurations from the plurality of switch configurations toselectively activate or deactivate each of the plurality of switches inorder to transfer electrical energy from the input source of the powerstage to the load.

In accordance with these and other embodiments of the presentdisclosure, a power stage for producing an output voltage to a load mayinclude a power converter, a linear amplifier, and a controller. Thepower converter may include a plurality of switches arranged tosequentially operate in a plurality of switch configurations and anoutput for producing the output voltage comprising a first outputterminal and a second output terminal, wherein a first switch of theplurality of switches is coupled to the first output terminal and asecond switch of the plurality of switches is coupled to the secondoutput terminal. The linear amplifier may be coupled to the output. Thecontroller may be configured to control the linear amplifier to transferelectrical energy from the input source of the power stage to the loadin accordance with one or more least significant bits of a digital inputsignal control the power converter in accordance with bits of thedigital input signal other than the one or more least significant bitsto sequentially apply switch configurations from the plurality of switchconfigurations to selectively activate or deactivate each of theplurality of switches in order to transfer electrical energy from theinput source of the power stage to the load.

In accordance with these and other embodiments of the presentdisclosure, a method for producing an output voltage to a load mayinclude, in a power stage comprising a power converter having a powerinductor, a plurality of switches arranged to sequentially operate in aplurality of switch configurations, and an output for producing theoutput voltage comprising a first output terminal and a second outputterminal, wherein a first switch of the plurality of switches is coupledto the first output terminal and a second switch of the plurality ofswitches is coupled to the second output terminal: (i) in a first modeof operation of the power stage, enable a linear amplifier to transferelectrical energy from an input source of the power stage to the loadand disable the plurality of switches from transferring electricalenergy from the input source to the load; and (ii) in a second mode ofoperation of the power stage, sequentially enable the linear amplifierin accordance with a probability which is a function of the outputvoltage to transfer electrical energy from the input source of the powerstage to the load and sequentially apply switch configurations from theplurality of switch configurations to selectively activate or deactivateeach of the plurality of switches in order to transfer electrical energyfrom the input source of the power stage to the load.

In accordance with these and other embodiments of the presentdisclosure, a method for producing an output voltage to a load mayinclude, in a power stage comprising a power converter having a powerinductor, a plurality of switches arranged to sequentially operate in aplurality of switch configurations, and an output for producing theoutput voltage comprising a first output terminal and a second outputterminal, wherein a first switch of the plurality of switches is coupledto the first output terminal and a second switch of the plurality ofswitches is coupled to the second output terminal: (i) controlling thelinear amplifier to transfer electrical energy from the input source ofthe power stage to the load in accordance with one or more leastsignificant bits of a digital input signal; and (ii) controlling thepower converter in accordance with bits of the digital input signalother than the one or more least significant bits to sequentially applyswitch configurations from the plurality of switch configurations toselectively activate or deactivate each of the plurality of switches inorder to transfer electrical energy from the input source of the powerstage to the load.

Technical advantages of the present disclosure may be readily apparentto one skilled in the art from the figures, description and claimsincluded herein. The objects and advantages of the embodiments will berealized and achieved at least by the elements, features, andcombinations particularly pointed out in the claims.

It is to be understood that both the foregoing general description andthe following detailed description are examples and explanatory and arenot restrictive of the claims set forth in this disclosure.

BRIEF DESCRIPTION OF THE DRAWINGS

A more complete understanding of the present embodiments and advantagesthereof may be acquired by referring to the following description takenin conjunction with the accompanying drawings, in which like referencenumbers indicate like features, and wherein:

FIG. 1 illustrates an example speaker driver, as is known in therelevant art.

FIG. 2 illustrates an example personal audio device, in accordance withembodiments of the present disclosure;

FIG. 3 illustrates a block diagram of selected components of an exampleaudio integrated circuit of a personal audio device, in accordance withembodiments of the present disclosure;

FIG. 4 illustrates a block and circuit diagram of selected components ofan example switched mode amplifier, in accordance with embodiments ofthe present disclosure;

FIG. 5 illustrates a circuit diagram of selected components of anotherexample power converter, in accordance with embodiments of the presentdisclosure;

FIG. 6 illustrates a table setting forth switch configurations of thepower converter of FIG. 5 when operating in a single-ended boost mode,in accordance with embodiments of the present disclosure;

FIG. 7 illustrates an equivalent circuit diagram of selected componentsof the power converter of FIG. 5 operating in a charging phase of asingle-ended boost mode, in accordance with embodiments of the presentdisclosure;

FIG. 8 illustrates an equivalent circuit diagram of selected componentsof the power converter of FIG. 5 operating in a discharge phase of asingle-ended boost mode, in accordance with embodiments of the presentdisclosure;

FIG. 9 illustrates a table setting forth switch configurations of thepower converter of FIG. 5 when operating in a differential-outputbuck-boost mode, in accordance with embodiments of the presentdisclosure;

FIG. 10 illustrates an equivalent circuit diagram of selected componentsof the power converter of FIG. 5 operating in a charging phase of adifferential-output buck-boost mode, in accordance with embodiments ofthe present disclosure;

FIG. 11 illustrates an equivalent circuit diagram of selected componentsof the power converter of FIG. 5 operating in a discharge phase of adifferential-output buck-boost mode, in accordance with embodiments ofthe present disclosure;

FIG. 12 illustrates a table setting forth switch configurations of thepower converter of FIG. 5 when operating in a differential-output buckmode, in accordance with embodiments of the present disclosure;

FIG. 13 illustrates an equivalent circuit diagram of selected componentsof the power converter of FIG. 5 operating in a charging phase of adifferential-output buck mode, in accordance with embodiments of thepresent disclosure;

FIG. 14 illustrates an equivalent circuit diagram of selected componentsof the power converter of FIG. 5 operating in another charging phase ofa differential-output buck mode, in accordance with embodiments of thepresent disclosure;

FIG. 15 illustrates an equivalent circuit diagram of selected componentsof the power converter of FIG. 5 operating in a discharge phase of adifferential-output buck mode, in accordance with embodiments of thepresent disclosure;

FIG. 16 illustrates a table setting forth switch configurations of thepower converter of FIG. 5 when operating in a turn-around mode, inaccordance with embodiments of the present disclosure;

FIG. 17 illustrates an equivalent circuit diagram of selected componentsof the power converter of FIG. 5 operating in a charging phase of adifferential-output turn-around mode, in accordance with embodiments ofthe present disclosure;

FIG. 18 illustrates an equivalent circuit diagram of selected componentsof the power converter of FIG. 5 operating in another charging phase ofa differential-output turn-around mode, in accordance with embodimentsof the present disclosure;

FIG. 19 illustrates an equivalent circuit diagram of selected componentsof the power converter of FIG. 5 operating in a discharge phase of adifferential-output turn-around mode, in accordance with embodiments ofthe present disclosure;

FIG. 20 illustrates a table setting forth switch configurations of thepower converter of FIG. 5 when operating in a single-ended buck mode, inaccordance with embodiments of the present disclosure;

FIG. 21 illustrates an equivalent circuit diagram of selected componentsof the power converter of FIG. 5 operating in a charging phase of asingle-ended buck mode, in accordance with embodiments of the presentdisclosure;

FIG. 22 illustrates an equivalent circuit diagram of selected componentsof the power converter of FIG. 5 operating in a discharge phase of asingle-ended buck mode, in accordance with embodiments of the presentdisclosure;

FIG. 23 illustrates an equivalent circuit diagram of selected componentsof the power converter of FIG. 5 operating in another charging phase ofa single-ended buck mode, in accordance with embodiments of the presentdisclosure;

FIG. 24 illustrates an equivalent circuit diagram of selected componentsof the power converter of FIG. 5 operating in another discharge phase ofa single-ended buck mode, in accordance with embodiments of the presentdisclosure;

FIG. 25 illustrates the power converter of FIG. 5 including a linearamplifier implemented as a quadrant digital-to-analog converter, inaccordance with embodiments of the present disclosure;

FIG. 26 illustrates the power converter of FIG. 5 including a linearamplifier implemented as a hemispherical digital-to-analog converter, inaccordance with embodiments of the present disclosure;

FIG. 27 illustrates a circuit diagram of selected components of anotherexample power converter, in accordance with embodiments of the presentdisclosure;

FIG. 28 illustrates a graph of an example output voltage having asinusoidal waveform, the graph indicating example ranges for operationin the various operational modes of the power converter of FIG. 5, inaccordance with embodiments of the present disclosure;

FIG. 29 illustrates a block diagram of selected components of an exampleloop filter, in accordance with embodiments of the present disclosure;

FIG. 30 illustrates a block diagram of selected components of a powerconverter control, in accordance with embodiments of the presentdisclosure;

FIG. 31 illustrates a graph of an example function of a duty cycle of alinear amplifier versus an output voltage of a power stage in accordancewith embodiments of the present disclosure; and

FIG. 32 illustrates a block and circuit diagram of selected componentsof an example switched mode amplifier including an impedance estimator,in accordance with embodiments of the present disclosure.

DETAILED DESCRIPTION

FIG. 2 illustrates an example personal audio device 1, in accordancewith embodiments of the present disclosure. FIG. 2 depicts personalaudio device 1 coupled to a headset 3 in the form of a pair of earbudspeakers 8A and 8B. Headset 3 depicted in FIG. 2 is merely an example,and it is understood that personal audio device 1 may be used inconnection with a variety of audio transducers, including withoutlimitation, headphones, earbuds, in-ear earphones, and externalspeakers. A plug 4 may provide for connection of headset 3 to anelectrical terminal of personal audio device 1. Personal audio device 1may provide a display to a user and receive user input using a touchscreen 2, or alternatively, a standard liquid crystal display (LCD) maybe combined with various buttons, sliders, and/or dials disposed on theface and/or sides of personal audio device 1. As also shown in FIG. 2,personal audio device 1 may include an audio integrated circuit (IC) 9for generating an analog audio signal for transmission to headset 3and/or another audio transducer.

FIG. 3 illustrates a block diagram of selected components of an exampleaudio IC 9 of a personal audio device, in accordance with embodiments ofthe present disclosure. As shown in FIG. 3, a microcontroller core 18may supply a digital audio input signal DIG_IN to a digital-to-analogconverter (DAC) 14, which may convert the digital audio input signal toan analog signal V_(IN). DAC 14 may supply analog signal V_(IN) to anamplifier 16 which may amplify or attenuate audio input signal V_(IN) toprovide a differential audio output signal V_(OUT), which may operate aspeaker, headphone transducer, a line level signal output, and/or othersuitable output. In some embodiments, DAC 14 may be an integralcomponent of amplifier 16. A power supply 10 may provide the powersupply rail inputs of amplifier 16. In some embodiments, power supply 10may comprise a battery. Although FIGS. 2 and 3 contemplate that audio IC9 resides in a personal audio device, systems and methods describedherein may also be applied to electrical and electronic systems anddevices other than a personal audio device, including audio systems foruse in a computing device larger than a personal audio device, anautomobile, a building, or other structure.

FIG. 4 illustrates a block and circuit diagram of selected components ofan example switched mode amplifier 20, in accordance with embodiments ofthe present disclosure. In some embodiments, switched mode amplifier 20may implement all or a portion of amplifier 16 described with respect toFIG. 3. As shown in FIG. 4, switched mode amplifier 20 may comprise aloop filter 22, a converter controller 24, and a power converter 26.

Loop filter 22 may comprise any system, device, or apparatus configuredto receive an input signal (e.g., audio input signal V_(IN) or aderivative thereof) and a feedback signal (e.g., audio output signalV_(OUT), a derivative thereof, or other signal indicative of audiooutput signal V_(OUT)) and based on such input signal and feedbacksignal, generate a controller input signal to be communicated toconverter controller 24. In some embodiments, such controller inputsignal may comprise a signal indicative of an integrated error betweenthe input signal and the feedback signal, as is described in greaterdetail below with reference to FIGS. 6, 9 and 25. In other embodiments,such controller input signal may comprise a signal indicative of atarget current signal to be driven as an output current I_(OUT) to aload coupled to the output terminals of power converter 26, as describedin greater detail below with reference to FIGS. 26 and 27.

Converter controller 24 may comprise any system, device, or apparatusconfigured to, based on the controller input signal, sequentially selectamong operational modes of power converter 26 and based on a selectedoperational mode, communicate a plurality of control signals to powerconverter 26 to apply a switch configuration from a plurality of switchconfigurations of switches of power converter 26 to selectively activateor deactivate each of the plurality of switches in order to transferelectrical energy from a power supply V_(SUPPLY) to the load ofswitched-mode amplifier 20 in accordance with the selected operationalmode. Examples of operational modes and switch configurations associatedwith each are described in greater detail elsewhere in this disclosure.Example implementations of converter controller 24 are also described ingreater detail elsewhere in this disclosure. In addition, in someembodiments, converter controller 24 may control switches of a powerconverter 26 in order to regulate a common mode voltage of the outputterminals of power converter 26 to the maximum of a first voltageassociated with switched-mode amplifier 20 and a second voltageassociated with switched-mode amplifier 20. In some embodiments, thefirst voltage may comprise one-half of the supply voltage V_(SUPPLY). Inthese and other embodiments, the second voltage may comprise one-half ofoutput voltage V_(OUT), or another signal indicative of an expectedvoltage for output voltage V_(OUT) (e.g, input voltage signal V_(N)).

Power converter 26 may receive at its input a voltage V_(SUPPLY) (e.g.,provided by power supply 10) at its input, and may generate at itsoutput audio output signal V_(OUT). Although not explicitly shown inFIG. 3, in some embodiments, voltage V_(SUPPLY) may be received viainput terminals including a positive input terminal and a negative inputterminal which may be coupled to a ground voltage. As described ingreater detail in this disclosure, power converter 26 may comprise apower inductor and a plurality of switches that are controlled bycontrol signals received from converter controller 24 in order toconvert voltage V_(SUPPLY) to audio output signal V_(OUT), such thataudio output signal V_(OUT) is a function of the input signal to loopfilter 22. Examples of power converter 26 are described in greaterdetail elsewhere in this disclosure.

FIG. 5 illustrates a circuit diagram of selected components of anexample power converter 26, in accordance with embodiments of thepresent disclosure. In some embodiments, power converter 26 depicted inFIG. 5 may implement all or a portion of power converter 26 describedwith respect to FIG. 4. As shown in FIG. 5, power converter 26 mayreceive at its input a voltage V_(SUPPLY) (e.g., provided by powersupply 10) at input terminals, including a positive input terminal and anegative input terminal which may be coupled to a ground voltage, andmay generate at its output a differential output voltage V_(OUT). Powerconverter 26 may comprise a power inductor 62 and plurality of switches51-60. Power inductor 62 may comprise any passive two-terminalelectrical component which resists changes in electrical current passingthrough it and such that when electrical current flowing through itchanges, a time-varying magnetic field induces a voltage in powerinductor 62, in accordance with Faraday's law of electromagneticinduction, which opposes the change in current that created the magneticfield.

Each switch 51-60 may comprise any suitable device, system, or apparatusfor making a connection in an electric circuit when the switch isenabled (e.g., closed or on) and breaking the connection when the switchis disabled (e.g., open or off) in response to a control signal receivedby the switch. For purposes of clarity and exposition, control signalsfor switches 51-60 (e.g., control signals communicated from convertercontroller 24) are not depicted although such control signals would bepresent to selectively enable and disable switches 51-60. In someembodiments, a switch 51-60 may comprise an n-typemetal-oxide-semiconductor field-effect transistor. Switch 51 may becoupled between the positive input terminal and a first terminal ofpower inductor 62. Switch 52 may be coupled between a second terminal ofpower inductor 62 and ground. Switch 53 may be coupled between apositive terminal of the output of power converter 26 and a secondterminal of power inductor 62. Switch 54 may be coupled between anegative terminal of the output of power converter 26 and the firstterminal of power inductor 62. Switch 55 may be coupled between anegative terminal of the output of power converter 26 and the secondterminal of power inductor 62. Switch 56 may be coupled between apositive terminal of the output of power converter 26 and the firstterminal of power inductor 62. Switch 57 may be coupled between theground voltage and the first terminal of power inductor 62. Switch 58may be coupled between the negative terminal of the output of powerconverter 26 and the ground voltage. Switch 59 may be coupled betweenthe positive terminal of the output of power converter 26 and the groundvoltage. Switch 60 may be coupled between the positive input terminaland the second terminal of power inductor 62.

In addition to switches 51-60 and power inductor 62, power converter 26may include a first output capacitor 66 coupled between the positiveterminal of the output of power converter 26 and the ground voltage anda second output capacitor 68 coupled between the negative terminal ofthe output of power converter 26 and the ground voltage. Each outputcapacitor 66 and 68 may comprise a passive two-terminal electricalcomponent used to store energy electrostatically in an electric field,and may generate a current in response to a time-varying voltage acrossthe capacitor.

As shown in FIG. 5, power converter 26 may in some embodiments comprisea linear amplifier 70. Functionality of power converter 26 is describedin greater detail elsewhere in this disclosure for those embodimentsincluding linear amplifier 70.

As described above, a power converter 26 may operate in a plurality ofdifferent operational modes, and may sequentially operate in a number ofswitch configurations under each operational mode. The plurality ofmodes may include, without limitation, a single-ended boost mode, adifferential-output buck-boost mode, a differential-output buck mode,and a low-voltage mode.

Power converter 26 may operate in a single-ended boost mode when outputvoltage V_(OUT) has a magnitude significantly larger than the supplyvoltage V_(SUPPLY) (e.g., |V_(OUT)|>V_(SUPPLY)=2V). FIG. 6 illustrates atable setting forth switch configurations of power converter 26 whenoperating in the single-ended boost mode, in accordance with embodimentsof the present disclosure. As shown in FIG. 6, when output voltageV_(OUT) is positive, and during a charging phase T1 of power converter26, converter controller 24 may enable switches 51, 52, and 58 of powerconverter 26, with such switch configuration resulting in the equivalentcircuit depicted in FIG. 7. In such switch configuration, power inductor62 may be charged via a current flowing between the power supply (e.g.,power supply 10) and ground. When output voltage V_(OUT) is positive,and during a discharge phase T2 of power converter 26, convertercontroller 24 may enable switches 51, 53, and 58 of power converter 26,with such switch configuration resulting in the equivalent circuitdepicted in FIG. 8. In such switch configuration, power inductor 62 maybe discharged, with charge transferred from the power supply (e.g.,power supply 10) to the positive terminal of the output of powerconverter 26. Similarly, when output voltage V_(OUT) is negative, andduring the charging phase T1 of power converter 26, converter controller24 may enable switches 51, 52, and 59 of power converter 26, wherein inaccordance with such switch configuration, power inductor 62 may becharged via a current flowing between the power supply (e.g., powersupply 10) and ground. In addition, when output voltage V_(OUT) isnegative, and during the discharge phase T2 of power converter 26,converter controller 24 may enable switches 51, 55, and 59 of powerconverter 26, wherein in accordance with such switch configuration,power inductor 62 may be discharged, with charge transferred from thepower supply (e.g., power supply 10) to the negative terminal of theoutput of power converter 26.

Notably, in the boost configuration, one of either of the terminals ofthe output of power converter 26 remains grounded in order to providefor operation in the boost mode, thus allowing power converter 26 to actas a boost converter when in the boost mode.

In some embodiments, it may be desirable to operate in a continuouscurrent mode (CCM) as opposed to a discontinuous current mode (DCM) whenoperating power converter 26 in the single-ended boost mode. Thispreference is because a CCM boost converter may have lowerroot-means-square (e.g., ripple) currents compared to a correspondingDCM boost converter.

For an input voltage signal V_(I) to loop filter 22, loop filter 22 maygenerate a target current signal I_(TGT) as the controller input signalwhich may be given by I_(TGT)=V_(I)/R_(OUT), where R_(OUT) is animpedance of a load at the output of power converter 26. A duration ofcharging phase T1 may be given by T1=D×TT, where D is a unitlessvariable given by D=1−(V_(SUPPLY)/V_(I)) and TT is a switching period ofpower converter 26 which is the sum of the durations of the chargingphase T1 and the transfer phase T2 (e.g., TT=T1+T2). A change in powerinductor current I_(L) occurring during charging phase T1 may be givenby ΔI_(L)=T1×(V_(SUPPLY)/L) where L is an inductance of power inductor62. A minimum inductor current I_(min) may be given by:I _(min)=[2×TT×I _(TGT)×(V _(SUPPLY) −V _(I))/L−ΔI _(L) ²]/2×ΔI _(L)and a peak current I_(pk) for inductor current I_(L) may be given asI_(pk)=I_(min)+ΔI_(L).

Power converter 26 may operate in a differential-output buck-boost modewhen output voltage V_(OUT) has a magnitude lower than that for whichthe single-ended boost mode is appropriate (e.g.,|V_(OUT)|<V_(SUPPLY)+2V) but higher than a particular thresholdmagnitude (e.g., |V_(OUT)|>3V) for which the duration of a chargingphase T1 becomes too small to operate power converter 26 in a buck-boostmode. FIG. 9 illustrates a table setting forth switch configurations ofpower converter 26 when operating in the differential-output buck-boostmode, in accordance with embodiments of the present disclosure. As shownin FIG. 9, when output voltage V_(OUT) is positive, and during acharging phase T1 of power converter 26, converter controller 24 mayenable switches 51 and 52 of power converter 26, with such switchconfiguration resulting in the equivalent circuit depicted in FIG. 10.In such switch configuration, power inductor 62 may be charged via acurrent flowing between the power supply (e.g., power supply 10) andground. When output voltage V_(OUT) is positive, and during a dischargephase T2 of power converter 26, converter controller 24 may enableswitches 53 and 54 of power converter 26, with such switch configurationresulting in the equivalent circuit depicted in FIG. 11. In such switchconfiguration, power inductor 62 may be discharged, with chargetransferred from the negative terminal of the output of power converter26 to the positive terminal of the output of power converter 26.Similarly, when output voltage V_(OUT) is negative, and during thecharging phase T1 of power converter 26, converter controller 24 mayenable switches 51 and 52 of power converter 26, wherein in accordancewith such switch configuration, power inductor 62 may be charged via acurrent flowing between the power supply (e.g., power supply 10) andground. In addition, when output voltage V_(OUT) is negative, and duringthe discharge phase T2 of power converter 26, converter controller 24may enable switches 55 and 56 of power converter 26, wherein inaccordance with such switch configuration, power inductor 62 may bedischarged, with charge transferred from the positive terminal of theoutput of power converter 26 to the negative terminal of the output ofpower converter 26.

Thus, in the differential-output buck-boost mode, power inductor 62 maybe charged from V_(SUPPLY) to ground during charging phases T1, and indischarging phases T2, power inductor 62 may be coupled across theoutput terminals of a load at the output of power converter 26 in orderto discharge power inductor 62 and create a differential output.Coupling power inductor 62 across the output terminals in a differentialoutput fashion may lead to a greater charge differential betweencapacitors 66 and 68 than would be in a single-ended configuration(e.g., with one of the output terminals grounded). Thus, lower powerinductor peak currents may be required to achieve the same outputcurrent.

Within the output voltage range of operation for the differential-outputbuck-boost mode, power converter 26 may operate in CCM for larger outputvoltages (e.g., 7V<V_(OUT)<V_(SUPPLY)+2V) and DCM for smaller outputvoltages (e.g., 3V<V_(OUT)<7V). In DCM, peak current I_(pk) of powerinductor 62 may be given by:

$I_{pk} = \sqrt{\frac{2 \times I_{TGT} \times V_{OUT} \times {TT}}{L}}$where TT is a switching period of power converter 26.

In CCM, a duration of charging phase T1 may be given by T1=D×TT, where Dis a unitless variable given by D=V_(OUT)/(V_(OUT)+V_(SUPPLY)) and TT isa switching period of power converter 26 which is the sum of thedurations of the charging phase T1 and the transfer phase T2 (e.g.,TT=T1+T2). A change in power inductor current I_(L) occurring duringcharging phase T1 may be given by ΔI_(L)=T1×(V_(SUPPLY)/L). A minimuminductor current I_(min) may be given by:I _(min) =[I _(OUT) ×TT×V _(OUT) /L−ΔI _(L) ²/2]/ΔI _(L)and a peak current I_(pk) for inductor current I_(L) may be given asI_(pk)=I_(min)+ΔI_(L).

Power converter 26 may operate in a differential-output buck mode whenoutput voltage V_(OUT) has a magnitude lower than that for which theduration of a charging phase T1 becomes too small to operate powerconverter in a buck-boost mode (e.g., |V_(OUT)|<3V) and a magnitudehigher than for which the duration of a charging phase T1 becomes toosmall (e.g. |V_(OUT)|>1V) to operate power converter 26 in a buck mode.FIG. 12 illustrates a table setting forth switch configurations of powerconverter 26 when operating in the differential-output buck-boost mode,in accordance with embodiments of the present disclosure. As shown inFIG. 12, in the differential-output buck mode, switch configurations maynot only be based on the polarity of output voltage V_(OUT), but also onwhether the common-mode voltage of the positive output terminal and thenegative output terminal of power converter 26 is to be increased ordecreased to regulate the common-mode voltage at a desired level, asshown in the column with the heading “CM” in FIG. 12. For example, insome embodiments, converter controller 24 may control switches of powerconverter 26 in order to regulate the common mode to a voltageassociated with switched-mode amplifier 20. In some embodiments, thevoltage may comprise one-half of the supply voltage V_(SUPPLY).

As shown in FIG. 12, during a charging phase T1 of power converter 26,when output voltage V_(OUT) is positive and the common-mode voltage ofthe output terminals is to be increased, converter controller 24 mayenable switches 51 and 53 of power converter 26, with such switchconfiguration resulting in the equivalent circuit depicted in FIG. 13.In such switch configuration, power inductor 62 may be charged via acurrent flowing between the power supply (e.g., power supply 10) and thepositive terminal of the output of power converter 26, thus generating apositive output voltage V_(OUT) and increasing the common-mode voltageby increasing the electrical charge on capacitor 66. On the other hand,during a charging phase T1 of power converter 26, when output voltageV_(OUT) is positive and the common-mode voltage of the output terminalsis to be decreased, converter controller 24 may enable switches 52 and54 of power converter 26, with such switch configuration resulting inthe equivalent circuit depicted in FIG. 14. In such switchconfiguration, power inductor 62 may be charged via a current flowingbetween the negative terminal of the output of power converter 26 andground, thus generating a positive output voltage V_(OUT) and decreasingcommon-mode voltage by decreasing the electrical charge on capacitor 68.During a discharge phase T2 of power converter 26, when target currentI_(TGT) is positive and regardless of whether the common-mode voltage ofthe output terminals is to be increased or decreased, convertercontroller 24 may enable switches 53 and 54 of power converter 26, withsuch switch configuration resulting in the equivalent circuit depictedin FIG. 15. In such switch configuration, power inductor 62 may bedischarged, with charge transferred from the negative terminal of theoutput of power converter 26 to the positive terminal of the output ofpower converter 26 in order to provide a positive output voltage V_(OUT)while maintaining the same common-mode voltage.

Similarly, during a charging phase T1 of power converter 26, when outputvoltage V_(OUT) is negative and the common-mode voltage of the outputterminals is to be increased, converter controller 24 may enableswitches 51 and 55 of power converter 26. In such switch configuration,power inductor 62 may be charged via a current flowing between the powersupply (e.g., power supply 10) and the negative terminal of the outputof power converter 26, thus generating a negative output voltage V_(OUT)and increasing the common-mode voltage by increasing the electricalcharge on capacitor 68. On the other hand, during a charging phase T1 ofpower converter 26, when output voltage V_(OUT) is negative and thecommon-mode voltage of the output terminals is to be decreased,converter controller 24 may enable switches 52 and 56 of power converter26. In such switch configuration, power inductor 62 may be charged via acurrent flowing between the positive terminal of the output of powerconverter 26 and ground, thus generating a negative output voltageV_(OUT) and decreasing common-mode voltage by decreasing the electricalcharge on capacitor 66. During a discharge phase T2 of power converter26, when output voltage V_(OUT) is negative and regardless of whetherthe common-mode voltage of the output terminals is to be increased ordecreased, converter controller 24 may enable switches 55 and 56 ofpower converter 26. In such switch configuration, power inductor 62 maybe discharged, with charge transferred from the positive terminal of theoutput of power converter 26 to the negative terminal of the output ofpower converter 26 in order to provide a negative output voltage V_(OUT)while maintaining the same common-mode voltage.

Thus, during charging phases T1, converter controller 24 may cause powerconverter 26 to couple a capacitor 66 or 68 to supply voltage V_(SUPPLY)or ground to increase or decrease the total amount of charge incapacitors 66 and 68 in order to regulate common-mode voltage of theoutput terminals. On the other hand, discharge phases T2 of convertercontroller 24 may cause power converter 26 to couple a power inductor 62across the output terminals, which may redistribute charge betweencapacitors 66 and 68. Accordingly, in the differential-output buck mode,power converter 26 uses common-mode voltage at the output to createdifferential output voltage V_(OUT), as the duration of charging phaseT1 may determine the common mode voltage and differential voltageV_(OUT) while the duration of discharge phase T2 may additionallydetermine the differential voltage V_(OUT). As compared to other modesof operation, the differential-output buck mode provides for efficientcharge transfer as charge is pushed to an output capacitor 66 or 68during charging phase T1 and redistributed between output capacitors 66and 68 during discharge phase T2. Because of such charge-transferscheme, lower peak currents through power inductor 62 may be necessaryto transfer charge as compared to other modes. Also, root-mean-squarecurrent through switch 51 may be reduced as it is not exercised as muchas it is in other modes of operation, which may minimize powerdissipation of switch 51. Common-mode voltage at the output terminalsmay also be well-controlled, as common-mode control is achieved bycoupling an output capacitor 66 or 68 to supply voltage V_(SUPPLY) orground through power inductor 62.

When operating in the differential-output buck mode, power converter 26may typically operate in DCM, unless power inductor 62 has a very highinductance (e.g., greater than 500 nH). In DCM, peak current I_(pk) ofpower inductor 62 may be given by:

$I_{pk} = \sqrt{\frac{2 \times I_{TGT} \times V_{OUT} \times \left( {V_{SUPPLY} - V_{OUT}} \right) \times {TT}}{L \times V_{SUPPLY}}}$where TT is a switching period of power converter 26.

In CCM, a duration of charging phase T1 may be given by T1=D×TT, where Dis a unitless variable given by D=V_(OUT)/(V_(OUT)+V_(SUPPLY)) and TT isa switching period of power converter 26 which is the sum of thedurations of the charging phase T1 and the transfer phase T2 (e.g.,TT=T1+T2). A change in power inductor current I_(L) occurring duringcharging phase T1 may be given by ΔI_(L)=T1×(V_(SUPPLY)−V_(OUT))/2 L. Aminimum inductor current I_(min) may be given by:I _(min) =[I _(OUT) ×TT×(V _(SUPPLY) −V _(OUT))×TT/(L×V _(SUPPLY))−ΔI_(L) ²/2]/ΔI _(L)and a peak current I_(pk) for inductor current I_(L) may be given asI_(pk)=I_(min)+ΔI_(L).

Power converter 26 may operate in a low-voltage mode in order to allowoutput voltage V_(OUT) to cross zero, as the differential-output buckmode and operational modes discussed above may not be capable ofeffectuating a polarity change in output voltage V_(OUT). Accordingly,when output voltage V_(OUT) has a magnitude lower than a particularthreshold (e.g., |V_(OUT)|<1V), power converter 26 may operate in thelow-voltage mode. As described below, the low-voltage mode may beimplemented in one of a plurality of ways, including a single-ended buckmode and a linear amplifier mode.

Power converter 26 may transition to operation in a differential-outputturn-around mode from the differential-output buck mode when, whileoperating in the differential-output buck mode, output voltage V_(OUT)has a polarity opposite that of a target voltage V_(TGT) for outputvoltage V_(OUT) wherein target voltage V_(TGT) corresponds to inputsignal INPUT. In such a situation, output voltage V_(OUT) may need toeffectively change polarity in a quick fashion, which may not bepossible using any of the operational modes described above. FIG. 16illustrates a table setting forth switch configurations of powerconverter 26 when operating in the differential-output turn-around mode,in accordance with embodiments of the present disclosure. As shown inFIG. 16, in the differential-output turn-around mode, switchconfigurations may not only be based on the polarities of output voltageV_(OUT) and target voltage V_(TGT), but also on whether the common-modevoltage of the positive output terminal and the negative output terminalof power converter 26 is to be increased or decreased to regulate thecommon-mode voltage at a desired level, as shown in the column with theheading “CM” in FIG. 16. For example, in some embodiments, convertercontroller 24 may control switches of power converter 26 in order toregulate the common mode to a voltage associated with switched-modeamplifier 20. In some embodiments, the voltage may comprise one-half ofthe supply voltage V_(SUPPLY).

As shown in FIG. 16, during a charging phase T1 of power converter 26,when output voltage V_(OUT) is negative, target voltage V_(TGT) ispositive (meaning output voltage V_(OUT) needs to switch from a negativeto a positive polarity), and the common-mode voltage of the outputterminals is to be increased, converter controller 24 may enableswitches 51 and 53 of power converter 26, with such switch configurationresulting in the equivalent circuit depicted in FIG. 17. In such switchconfiguration, power inductor 62 may be charged via a current flowingbetween the power supply (e.g., power supply 10) and the positiveterminal of the output of power converter 26, thus generating anincreasing output voltage V_(OUT) and increasing the common-mode voltageby increasing the electrical charge on capacitor 66. On the other hand,during a charging phase T1 of power converter 26, when output voltageV_(OUT) is negative, target voltage V_(TGT) is positive (meaning outputvoltage V_(OUT) needs to switch from a negative to a positive polarity),and the common-mode voltage of the output terminals is to be decreased,converter controller 24 may enable switches 52 and 54 of power converter26, with such switch configuration resulting in the equivalent circuitdepicted in FIG. 18. In such switch configuration, power inductor 62 maybe charged via a current flowing between the negative terminal of theoutput of power converter 26 and ground, thus generating an increasingoutput voltage V_(OUT) and decreasing common-mode voltage by decreasingthe electrical charge on capacitor 68. During a discharge phase T2 ofpower converter 26, when output voltage V_(OUT) is negative, targetvoltage V_(TGT) is positive (meaning output voltage V_(OUT) needs toswitch from a negative to a positive polarity), and regardless ofwhether the common-mode voltage of the output terminals is to beincreased or decreased, converter controller 24 may enable switches 53and 57 of power converter 26, with such switch configuration resultingin the equivalent circuit depicted in FIG. 19. In such switchconfiguration, power inductor 62 may be discharged, with chargetransferred from the ground to the positive terminal of the output ofpower converter 26 in order to provide an increasing output voltageV_(OUT).

Similarly, during a charging phase T1 of power converter 26, when outputvoltage V_(OUT) is positive, target voltage V_(TGT) is negative (meaningoutput voltage V_(OUT) needs to switch from a positive to a negativepolarity), and the common-mode voltage of the output terminals is to beincreased, converter controller 24 may enable switches 51 and 55 ofpower converter 26. In such switch configuration, power inductor 62 maybe charged via a current flowing between the power supply (e.g., powersupply 10) and the negative terminal of the output of power converter26, thus generating a decreasing output voltage V_(OUT) and increasingthe common-mode voltage by increasing the electrical charge on capacitor68. On the other hand, during a charging phase T1 of power converter 26,when output voltage V_(OUT) is positive, target voltage V_(TGT) isnegative (meaning output voltage V_(OUT) needs to switch from a positiveto a negative polarity), and the common-mode voltage of the outputterminals is to be decreased, converter controller 24 may enableswitches 52 and 56 of power converter 26. In such switch configuration,power inductor 62 may be charged via a current flowing between thepositive terminal of the output of power converter 26 and ground, thusgenerating a decreasing output voltage V_(OUT) and decreasingcommon-mode voltage by decreasing the electrical charge on capacitor 66.During a discharge phase T2 of power converter 26, voltage V_(OUT) ispositive, target voltage V_(TGT) is negative (meaning output voltageV_(OUT) needs to switch from a positive to a negative polarity), andregardless of whether the common-mode voltage of the output terminals isto be increased or decreased, converter controller 24 may enableswitches 55 and 57 of power converter 26. In such switch configuration,power inductor 62 may be discharged, with charge transferred from theground to the negative terminal of the output of power converter 26 inorder to provide a decreasing output voltage V_(OUT).

Thus, during charging phases T1, converter controller 24 may cause powerconverter 26 to couple a capacitor 66 or 68 to supply voltage V_(SUPPLY)or ground to increase or decrease the total amount of charge incapacitors 66 and 68 in order to regulate common-mode voltage of theoutput terminals. On the other hand, discharge phases T2 of convertercontroller 24 may cause power converter 26 to couple a power inductor 62between the ground and one of the output terminals, to increase ordecrease output voltage V_(OUT). Accordingly, in the differential-outputturn-around mode, power converter 26 uses common-mode voltage at theoutput to create differential output voltage V_(OUT), as the duration ofcharging phase T1 may determine the common mode voltage and differentialvoltage V_(OUT) while the duration of discharge phase T2 mayadditionally determine the differential voltage V_(OUT).

FIG. 20 illustrates a table setting forth switch configurations of powerconverter 26 when operating in the single-ended buck mode, in accordancewith embodiments of the present disclosure. As shown in FIG. 20, whentarget voltage V_(TGT) is positive and the common-mode voltage of theoutput terminals is to be increased, power converter 26 may have acharging phase T1 in which converter controller 24 enables switches 51and 53 (as shown in the equivalent circuit depicted in FIG. 21),followed immediately by a discharge phase T2 in which convertercontroller 24 enables switches 54 and 60 of power converter 26 (as shownin the equivalent circuit depicted in FIG. 22). In such charging phaseT1, power inductor 62 may be charged via a current flowing between thepower supply (e.g., power supply 10) and the positive terminal of theoutput of power converter 26, thus generating an increasing outputvoltage V_(OUT) and increasing the common-mode voltage by increasing theelectrical charge on capacitor 66. In such discharge phase T2, powerinductor 62 may be discharged, with charge transferred from the negativeterminal of the output of power converter 26 to the power supply inorder to provide an increasing output voltage V_(OUT). Discharge phaseT2 may have the effect of decreasing the common-mode voltage, but thenet effect of charging phase T1 and discharge phase T2 may be anincrease in common-mode voltage.

Also as shown in FIG. 20, when target voltage V_(TGT) is positive andthe common-mode voltage of the output terminals is to be decreased,power converter 26 may have a charging phase T1 in which convertercontroller 24 enables switches 52 and 54 (as shown in the equivalentcircuit depicted in FIG. 23), followed immediately by a discharge phaseT2 in which converter controller 24 enables switches 53 and 57 of powerconverter 26 (as shown in the equivalent circuit depicted in FIG. 24).In such charging phase T1, power inductor 62 may be charged via acurrent flowing between the negative terminal of the output of powerconverter 26 and ground, thus generating an increasing output voltageV_(OUT) and decreasing common-mode voltage by decreasing the electricalcharge on capacitor 68. In such discharge phase T2, power inductor 62may be discharged, with charge transferred from the ground to thepositive terminal of the output of power converter 26 in order toprovide an increasing output voltage V_(OUT). Discharge phase T2 mayhave the effect of increasing the common-mode voltage, but the neteffect of charging phase T1 and discharge phase T2 may be a decrease incommon-mode voltage.

Similarly, when target voltage V_(TGT) is positive and the common-modevoltage of the output terminals is to be increased, power converter 26may have a charging phase T1 in which converter controller 24 enablesswitches 51 and 55, followed immediately by a discharge phase T2 inwhich converter controller 24 enables switches 56 and 60 of powerconverter 26. In such charging phase T1, power inductor 62 may becharged via a current flowing between the power supply (e.g., powersupply 10) and the negative terminal of the output of power converter26, thus generating a decreasing output voltage V_(OUT) and increasingthe common-mode voltage by increasing the electrical charge on capacitor68. In such discharge phase T2, power inductor 62 may be discharged,with charge transferred from the positive terminal of the output ofpower converter 26 to the power supply in order to provide a decreasingoutput voltage V_(OUT). Discharge phase T2 may have the effect ofdecreasing the common-mode voltage, but the net effect of charging phaseT1 and discharge phase T2 may be an increase in common-mode voltage.

On the other hand, when target voltage V_(TGT) is positive and thecommon-mode voltage of the output terminals is to be increased, powerconverter 26 may have a charging phase T1 in which converter controller24 enables switches 52 and 56, followed immediately by a discharge phaseT2 in which converter controller 24 enables switches 55 and 57 of powerconverter 26. In such charging phase T1, power inductor 62 may becharged via a current flowing between the positive terminal of theoutput of power converter 26 and ground, thus generating a decreasingoutput voltage V_(OUT) and decreasing common-mode voltage by decreasingthe electrical charge on capacitor 66. In such discharge phase T2, powerinductor 62 may be discharged, with charge transferred from the groundto the negative terminal of the output of power converter 26 in order toprovide a decreasing output voltage V_(OUT). Discharge phase T2 may havethe effect of increasing the common-mode voltage, but the net effect ofcharging phase T1 and discharge phase T2 may be a decrease incommon-mode voltage.

In the linear amplifier mode, linear amplifier 70 may receive a digitallinear amplifier input signal from converter controller 24, loop filter22, or elsewhere within switched mode amplifier 20. For example, in someembodiments, digital linear amplifier input signal may comprise anoutput of a quantizer of loop filter 22. To provide for fine resolutionin the low-voltage mode of output voltages at magnitudes lower than theoperational range of the differential-output buck mode, power converter26 may operate in a linear amplifier mode, in which linear amplifier 70of FIG. 5, operating in effect as a digital-to-analog converter (DAC),may be used to convert the digital linear amplifier control signal(which may be indicative of a desired output current I_(OUT))communicated from loop filter 22, converter controller 24, or elsewherewithin switched mode amplifier into an analog current driven to a loadcoupled between output terminals of power converter 26. Linear amplifier70, which is shown as a current source in FIG. 5, may comprise anysystem, device, or apparatus configured to generate a current inresponse to an input signal.

An example embodiment for linear amplifier 70 is depicted in FIG. 25, inwhich linear amplifier 70 is embodied as a current-mode quadrant DAChaving variable current sources 70A, 70B, 70C, and 70D. In the linearamplifier mode, when output voltage V_(OUT) is positive, current sources70A and 70B may be enabled to deliver a current to a load at the outputof power converter 26 with a magnitude to generate the desired positiveoutput voltage V_(OUT). Conversely, when output voltage V_(OUT) isnegative, current sources 70C and 70D may be enabled to deliver acurrent to a load at the output of power converter 26 with a magnitudeto generate the desired negative output voltage V_(OUT).

Another example embodiment for linear amplifier 70 is shown in FIG. 26,in which linear amplifier 70 is embodied as a current-mode hemisphericalDAC having variable current sources 70E and 70F and switches 71A, 71B,71C, and 71D. In the linear amplifier mode, when output voltage V_(OUT)is positive, switches 71A and 71B may be enabled (e.g., closed or on)and switches 71C and 71D may be disabled (e.g, open or off) to deliver acurrent to a load at the output of power converter 26 with a magnitudeto generate the desired positive output voltage V_(OUT). Conversely,when output voltage V_(OUT) is negative, switches 71C and 71D may beenabled (e.g., closed or on) and switches 71A and 71B may be disabled(e.g, open or off) to deliver a current to a load at the output of powerconverter 26 with a magnitude to generate the desired negative outputvoltage V_(OUT).

In some embodiments, converter controller 24 may control switches ofpower converter 26 such that the switches perform synchronousrectification, wherein all switches of power converter 26 are controlled(e.g., disabled if inductor current I_(L) decrease to zero) in order toprevent inductor current I_(L) from decreasing below zero. In otherembodiments, power converter 26 may include a diode (e.g., with anodeterminal coupled to power inductor 62 and cathode terminal coupled toswitches 53 and 55) in order to prevent inductor current I_(L) fromdecreasing below zero.

FIG. 27 illustrates a circuit diagram of selected components of anotherexample power converter 26A, in accordance with embodiments of thepresent disclosure. Power converter 26A may, in some embodiments, beused as an alternative to power converter 26 depicted in FIG. 5, and mayin many respects, be mathematically equivalent to power converter 26depicted in FIG. 5 and/or operate in a similar manner to power converter26 depicted in FIG. 5. As shown in FIG. 27, power converter 26A mayreceive at its input a voltage V_(SUPPLY) (e.g., provided by powersupply 10) at input terminals, including a positive input terminal and anegative input terminal which may be coupled to a ground voltage, andmay generate at its output a differential output voltage V_(OUT). Powerconverter 26A may comprise a power inductor 62A, and a plurality ofswitches 51A-58A. Power converter 26A may also include across its outputterminals a linear amplifier 70X identical or similar to linearamplifier 70 of power amplifier 26. Power inductor 62A may comprise anypassive two-terminal electrical component which resists changes inelectrical current passing through it and such that when electricalcurrent flowing through it changes, a time-varying magnetic fieldinduces a voltage in power inductor 62A, in accordance with Faraday'slaw of electromagnetic induction, which opposes the change in currentthat created the magnetic field.

Each switch 51A-58A may comprise any suitable device, system, orapparatus for making a connection in an electric circuit when the switchis enabled (e.g., closed or on) and breaking the connection when theswitch is disabled (e.g., open or off) in response to a control signalreceived by the switch. For purposes of clarity and exposition, controlsignals for switches 51A-58A (e.g., control signals communicated fromconverter controller 24) are not depicted although such control signalswould be present to selectively enable and disable switches 51A-58A. Insome embodiments, a switch 51A-58A may comprise an n-typemetal-oxide-semiconductor field-effect transistor. Switch 51A may becoupled between the positive input terminal and a first terminal ofpower inductor 62A. Switch 52A may be coupled between the positive inputterminal and a second terminal of power inductor 62A. Switch 53A may becoupled between the first terminal of power inductor 62A and the groundvoltage. Switch 54A may be coupled between the second terminal of powerinductor 62A and the ground voltage. Switch 55A may be coupled betweenthe first terminal of power inductor 62A and a negative terminal of theoutput of power converter 26A. Switch 56A may be coupled between thesecond terminal of power inductor 62A and a positive terminal of theoutput of power converter 26A. Switch 57A may be coupled between thenegative terminal of the output of power converter 26A and the groundvoltage. Switch 58A may be coupled between the positive terminal of theoutput of power converter 26A and the ground voltage.

In addition to switches 51A-58A and power inductor 62A, power converter26A may include a first output capacitor 66A coupled between thepositive terminal of the output of power converter 26A and the groundvoltage and a second output capacitor 68A coupled between the negativeterminal of the output of power converter 26A and the ground voltage.Each output capacitor 66A and 68A may comprise a passive two-terminalelectrical component used to store energy electrostatically in anelectric field, and may generate a current in response to a time-varyingvoltage across the capacitor.

FIG. 28 illustrates a graph of an example output voltage V_(OUT) havinga sinusoidal waveform, the graph indicating example ranges for operationin the various operational modes of power converter 26. Thus, for afull-scale sinusoidal signal, power converter 26 may sequentiallyoperate in the low-voltage mode (e.g., single-ended buck, or linearamplifier mode), the differential-output buck mode, the differentialoutput buck-boost mode, the single-ended boost mode, the differentialoutput buck-boost mode, the differential-output buck mode, and thelow-voltage mode (e.g., single-ended buck, or linear amplifier mode) foreach half-cycle of output voltage V_(OUT). Although not shown in FIG.28, in some embodiments, while operating in the differential-output buckmode, power converter 26 may switch to operation in thedifferential-output turn-around mode, in order to change a signalpolarity of the output voltage V_(OUT) in response to a target voltagecorresponding to input signal INPUT having an opposite polarity ofoutput voltage V_(OUT). In addition, in these and other embodiments, thelow-voltage mode may employ the differential-output turn-around mode ora similar mode (e.g., instead of the single-ended buck or linearamplifier mode) in order to operate at lower voltage magnitudes andchange the polarity of output voltage V_(OUT).

FIG. 29 illustrates a block diagram of selected components of an exampleloop filter 22, in accordance with embodiments of the presentdisclosure. In some embodiments, loop filter 22 depicted in FIG. 29 mayimplement all or a portion of loop filter 22 described with respect toFIG. 4.

Loop filter 22 may comprise a delta-sigma filter or similar filter whichmay have the function of moving quantization errors outside the audioband. Loop filter 22 may include an input summer 73 for generating adifference between an input signal (e.g., an analog voltage signalV_(IN)) and a feedback signal (e.g., output voltage V_(OUT)), and one ormore integrator stages 74, such that loop filter 22 operates as analogfilter of an error signal equal to the difference between the inputsignal and the feedback signal, and generates, at the output of outputsummer 75 a filtered analog signal to analog-to-digital converter (ADC)78 based on the input signal and the feedback signal. The inputs tooutput summer 75 may include the input signal as modified by afeed-forward gain coefficient K_(F) applied by a gain element 76, theoutputs of individual integrator stages 74 as each is modified by arespective integrator gain coefficient K₁, K₂, . . . , K_(N) applied bygain elements 76, and the output of a feedback digital-to-analogconverter 80 as modified by a delay-compensation coefficient K_(D)applied by a gain element 77 in order to compensate for excess loopdelay of loop filter 22.

ADC 78 may comprise any system, device, or apparatus for converting theanalog output signal generated by loop filter 22 (e.g., the output ofoutput summer 75) into an equivalent digital signal, which, in someembodiments, may represent a desired output voltage to be generated atthe output of switched mode amplifier 20 (e.g., across the terminalslabeled V_(OUT) in FIG. 5). Such digital signal or a derivative thereof(e.g., a current signal based on the input signal) may be communicatedto converter controller 24, such that converter controller 24 maycontrol switches of power converter 26 in accordance with a selectedmode corresponding to such quantized integrated error.

DAC 80 may comprise any suitable system, device, or apparatus configuredto convert the digital signal into an equivalent analog feedback signal.

FIG. 30 illustrates a block diagram of selected components of an exampleconverter controller 24A, in accordance with embodiments of the presentdisclosure. In some embodiments, converter controller 24A depicted inFIG. 30 may implement all or a portion of converter controller 24described with respect to FIG. 4. In the embodiments represented by FIG.30 the controller input signal received by converter controller 24A is atarget current signal I_(TGT). As shown in FIG. 30, converter controller24A may implement an ADC 82, a mode determiner 84, a peak currentcomputation block 86, a DAC 88, a peak current detector 90, a clock 92,a phase determiner 94, and a switch/linear amplifier controller 96.

ADC 82 may comprise any system, device, or apparatus configured toconvert analog output voltage V_(OUT) (or a derivative thereof) into anequivalent digital signal V_(OUT) _(_) _(DIG).

Mode determiner 84 may comprise any system, device, or apparatusconfigured to select a mode of operation from a plurality of modes ofoperation (e.g., single-ended boost mode, differential-output buck-boostmode, differential-output buck mode, low-voltage mode, etc.) based ondigital output voltage signal V_(OUT) _(_) _(DIG) (or another signalindicative of output voltage V_(OUT)) and/or a digital input voltagesignal V_(I) _(_) _(DIG) indicative of input voltage V_(IN). Forexample, mode determiner 82 may select the mode of operation based upona voltage range of digital output voltage signal V_(OUT) _(_) _(DIG),digital input voltage signal V_(I) _(_) _(DIG), or a signal derivativeor indicative thereof, such as analog feedback voltage V_(FB) describedin greater detail below with respect to FIG. 32 (e.g., selectsingle-ended boost mode for |V_(FB)|>14V, select differential-outputbuck-boost mode for 3V<|V_(FB)|<14V, select differential-output buckmode for 1V<|V_(FB)|<3V, and select the low-voltage mode for|V_(I)|<1V).

Peak current computation block 86 may comprise any system, device, orapparatus configured to compute a peak current I_(pk) to be driventhrough power inductor 62 during a switching cycle of power converter26. Such peak current I_(pk) may be calculated based on the selectedmode of operation, digital output voltage signal V_(OUT) _(_) _(DIG) (oranother signal indicative of output voltage V_(OUT)), supply voltageV_(SUPPLY), output current I_(OUT) (or another signal indicative ofoutput current I_(OUT)), and/or target current I_(TGT) in accordancewith the various equations for peak current I_(pk) set forth above.

DAC 88 may comprise any system, device, or apparatus configured toconvert a digital signal generated by peak current computation block 106indicative of peak current I_(pk) into an equivalent analog peak currentsignal I_(pk).

Peak current detector 90 may comprise any system, device, or apparatusconfigured to compare power inductor current I_(L) to the analog peakcurrent signal I_(pk) and generate an output signal indicative of thecomparison, thus providing an indication for when power inductor currentI_(L) has reached its desired peak current. Power inductor current I_(L)reaching its desired peak current may indicate the end of a chargingphase T1 and beginning of a transfer phase T2 of power converter 26.

Clock 92 may comprise any system, device, or apparatus configured togenerate a periodic timing signal indicative of an occurrence of orwithin a switching cycle of power converter 26. For example, a zerocrossing, edge, or other characteristic of a waveform generated by clock92 may indicate the beginning of a charging phase T1 of power converter26.

Phase determiner 94 may comprise any system, device, or apparatusconfigured to, based on the outputs of peak current detector 90 andclock 92, determine which phase (e.g., charging phase T1 or dischargephase T2) power converter 26 is to operate.

Switch/linear amplifier controller 96 may comprise any system, device,or apparatus configured to, based on the mode of operation, phase,polarity of digital input signal V_(I) _(_) _(DIG) (or another signalindicative of input voltage V_(IN) or output voltage V_(OUT)), and (forthe differential-output buck mode of power converter 26) a common-modevoltage V_(CM) of the output terminals of power converter 26, generateswitch control signals for controlling the switches of power converter26 and/or one or more control signals for controlling linear amplifier70.

Thus, during each switching cycle for converter controller 24A,converter controller 24A may select a mode of operation based on inputvoltage V_(IN) and output voltage V_(OUT), calculate a peak currentI_(pk) based on input voltage V_(IN), output voltage V_(OUT), targetcurrent signal I_(TGT), and/or output current I_(OUT), and useinformation regarding the selected mode and the phase of power converter26 to select a switch configuration to control the switches of powerconverter 26. In alternative embodiments, rather than operating as apeak current system as depicted in FIG. 28, converter controller 24 mayoperate as a time-based system based on measurements of supply voltageV_(SUPPLY), output voltage V_(OUT), and output current I_(OUT).

Thus, in the various embodiments disclosed herein, the choice ofsequence for switches of power converter 26 may be made consistent witha desired change in output voltage V_(OUT). By repeatedly increasing anddecreasing output voltage V_(OUT) in small steps, output voltage V_(OUT)may be made to follow, on average, the desired audio signal.Accordingly, quantization error present in output voltage V_(OUT) may bemoved outside the audio band in a manner similar to a delta-sigmamodulator.

In the foregoing discussion, it is contemplated that linear amplifier 70is used in a low-voltage mode of operation of power converter 26 inwhich output voltage V_(OUT) is below a particular threshold magnitudeof output voltage V_(OUT). However, in other embodiments, linearamplifier 70 may be operational to generate a current to outputterminals of power converter 26 at voltages above such thresholdmagnitude. For example, in some embodiments, converter controller 24 maybe able to, when output voltage V_(OUT) is greater than a thresholdmagnitude, sequentially operate switches 51-60 as described herein togenerate at least a portion of output voltage V_(OUT), and alsosequentially enable and disable linear amplifier 70 to deliverelectrical energy to a load at the output terminals of power converter26 in accordance with a probability (e.g., a duty cycle) which is afunction of output voltage V_(OUT). FIG. 31 illustrates a graph of anexample function of a duty cycle of linear amplifier 70 versus outputvoltage V_(OUT), representing a probability that amplifier 70 deliverselectrical energy to a load at the output terminals of power converter26 for given magnitudes of output voltage V_(OUT) For example, atmagnitudes of output voltage V_(OUT) below a threshold voltage V_(th1),linear amplifier 70 may have a 100% duty cycle, converter controller 24may disable operation of switches 51-60, and linear amplifier 70 maysupply the entirety of the electrical current required to generateoutput voltage V_(OUT). When the magnitude of output voltage V_(OUT)exceeds threshold voltage V_(th1), converter controller 24 may thenenable power converter 26 to sequentially apply switch configurationsfrom a plurality of switch configurations to selectively activate ordeactivate each of the plurality of switches 51-60 in order to transferelectrical energy to the load, while also enabling the linear amplifier70 to deliver electrical energy to the load in accordance with aprobability which is a function of output voltage v_(OUT). Above asecond threshold voltage V_(th2), the probability of amplifier 70 beingenabled may equal zero, such that converter controller 24 may completelydisable linear amplifier 70 from delivering electrical energy to theload but continue to control switches 51-60 of power converter 26 tosequentially apply switch configurations from the plurality of switchconfigurations to selectively activate or deactivate each of theplurality of switches 51-60 in order to transfer electrical energy tothe load.

As described above, the controller input signal generated by loop filter22 may serve as a digital input signal to the power stage comprisingconverter controller 24 and power converter 26, such that powerconverter 26 generates output voltage v_(OUT) responsive to such digitalinput signal (e.g., output voltage v_(OUT) is a function of such digitalinput signal). In some embodiments, converter controller 24 may controllinear amplifier 70 to deliver electrical energy to a load at the outputterminals of power converter 26 in accordance with one or more leastsignificant bits of the digital input signal and also control theplurality of switches 51-60 to transfer electrical energy to the load inaccordance with bits of the digital input signal other than the one ormore least significant bits. Accordingly, below a particular magnitudeof output voltage v_(OUT), output voltage v_(OUT) may be representedentirely by the one or more least significant bits of the digital inputsignal, in which case converter controller 24 may enable linearamplifier 70 to generate output voltage v_(OUT) as a function of thedigital input signal while disabling the switches 51-60 of powerconverter 26 from delivering electrical energy to the load. On the otherhand, above such particular magnitude of output voltage v_(OUT),converter controller 24 may enable linear amplifier 70 to generate aportion of output voltage v_(OUT) corresponding to the one or more leastsignificant bits of the digital input signal while controlling thesequential operation of switches 51-60 of power converter 26 to generatethe portion of output voltage v_(OUT) corresponding to bits of thedigital input signal other than the one or more least significant bits.

FIG. 32 illustrates a block and circuit diagram of selected componentsof an example switched mode amplifier 20B including an impedanceestimator 23, in accordance with embodiments of the present disclosure.In the embodiments represented by FIG. 32, switched mode amplifier 20Bmay operate as voltage feedback loop (e.g., a delta-sigma modulator)responsive to input voltage V_(I) and output voltage V_(OUT). Switchedmode amplifier 20B may be similar to switched mode amplifier 20 of FIG.4, except that switched mode amplifier 20B may also include impedanceestimator 23 and a current calculator 21 interfaced between loop filter22 and converter controller 24, and a differential amplifier 25 and acurrent sensor 27. Loop filter 22, converter controller 24, and powerconverter 26 may respectively comprise any suitable loop filters,converter controllers, and power converters, including withoutlimitation the various loop filters, converter controllers, and powerconverters disclosed herein. In the embodiments represented by FIG. 32,loop filter 22 may receive an input voltage V_(I) as its input andgenerate, based on input voltage V_(I) and an analog voltage feedbacksignal V_(FB), a target voltage signal V_(TGT) representative of avoltage to be applied as output voltage V_(OUT).

Impedance estimator 23 may comprise any system, device, or apparatus forestimating an impedance of a load at the output of switched modeamplifier 20B (e.g., across the terminals labeled V_(OUT) in FIG. 32).Impedance estimator 23 may estimate load impedance Z_(OUT) based on ameasured output current I_(OUT) and analog voltage feedback signalV_(FB) (or other signal indicative of output voltage V_(OUT)), andapplying Ohm's law to determine load impedance Z_(OUT) (e.g.,Z_(OUT)≈V_(FB)/I_(OUT)). In some embodiments, impedance estimator 23 maycomprise or implement an adaptive filter (e.g., a least-mean-squaresfilter) configured to adaptively minimize a difference between targetoutput voltage V_(TGT) of a load and an actual output voltage of theload (e.g., V_(OUT), V_(FB)), wherein target output voltage V_(TGT) isequal to an output voltage expected from applying target current signalI_(TGT) to the load assuming no variance of a nominal impedance of theload, and the actual output voltage at the load is the output voltage ofthe load generated by applying the output current (e.g., I_(OUT)) to theload. In these and other embodiments, impedance estimator 23 may beconfigured to determine impedance of a load at the output ofswitched-mode amplifier 20B as a function of a frequency of outputvoltage V_(OUT) and control target current signal I_(TGT) to compensatefor variance of the impedance as a function of the frequency. In theseand other embodiments, impedance estimator 23 may be configured tocontrol target current signal I_(TGT) to compensate for variance of theimpedance Z_(OUT) over time.

Current calculator 21 comprise any system, device, or apparatus forcalculating a target current I_(TGT) to be applied to the output load ofpower converter 26 based on target output voltage V_(TGT) generated byloop filter 22 and estimated load impedance Z_(OUT) generated byimpedance estimator 23, and applying Ohm's law to determine targetcurrent I_(TGT) (e.g., I_(TGT)≈V_(TGT)/Z_(OUT)).

Differential amplifier 25 may comprise any system, device, or apparatusconfigured to receive at its input terminals differential output voltageV_(OUT) and generate analog voltage feedback signal V_(FB) indicative ofdifferential output voltage V_(OUT).

Current sensor 27 may comprise any system, device, or apparatusconfigured to sense output current I_(OUT) and generate a signalindicative of such sensed output current.

Thus, switched-mode amplifier 20B may comprise a system which includesan impedance estimator 23 configured to estimate an impedance of a loadat the output of switched-mode amplifier 20B and a current calculator 21configured to generate a target current I_(TGT) based at least on aninput voltage V_(I) and the impedance. In some embodiments, currentcalculator 21 may be integral to impedance estimator 23 such thatimpedance estimator 23 includes both the functionality of impedanceestimator 23 and current calculator 21 depicted on FIG. 32. Such systemmay also include a voltage feedback loop (e.g., implemented bydifferential amplifier 25 and loop filter 22) responsive to a differencebetween the input voltage V_(I) and an output voltage of the load(represented by analog voltage feedback signal V_(FB)). Such system mayalso include a current controller (e.g., implemented by convertercontroller 24 and power converter 26) configured to, responsive to thevoltage feedback loop, impedance estimator 23, and the input voltageV_(I), generate an output current I_(OUT) to the load.

As used herein, absolute voltage values (e.g., 1V, 3V, 7V, 14V) aregiven merely as examples, and any other suitable voltages may be used todefine ranges of operation of the various power converter modesdescribed herein.

As used herein, when two or more elements are referred to as “coupled”to one another, such term indicates that such two or more elements arein electronic communication or mechanical communication, as applicable,whether connected indirectly or directly, with or without interveningelements.

This disclosure encompasses all changes, substitutions, variations,alterations, and modifications to the exemplary embodiments herein thata person having ordinary skill in the art would comprehend. Similarly,where appropriate, the appended claims encompass all changes,substitutions, variations, alterations, and modifications to theexemplary embodiments herein that a person having ordinary skill in theart would comprehend. Moreover, reference in the appended claims to anapparatus or system or a component of an apparatus or system beingadapted to, arranged to, capable of, configured to, enabled to, operableto, or operative to perform a particular function encompasses thatapparatus, system, or component, whether or not it or that particularfunction is activated, turned on, or unlocked, as long as thatapparatus, system, or component is so adapted, arranged, capable,configured, enabled, operable, or operative.

All examples and conditional language recited herein are intended forpedagogical objects to aid the reader in understanding the invention andthe concepts contributed by the inventor to furthering the art, and areconstrued as being without limitation to such specifically recitedexamples and conditions. Although embodiments of the present inventionshave been described in detail, it should be understood that variouschanges, substitutions, and alterations could be made hereto withoutdeparting from the spirit and scope of the disclosure.

What is claimed is:
 1. A power stage for producing an output voltage toa load, comprising: a power converter comprising: a plurality ofswitches arranged to sequentially operate in a plurality of switchconfigurations; and an output for producing the output voltagecomprising a first output terminal and a second output terminal, whereina first switch of the plurality of switches is coupled to the firstoutput terminal and a second switch of the plurality of switches iscoupled to the second output terminal; a linear amplifier coupled to theoutput; and a controller configured to: in a first mode of operation ofthe power stage, enable the linear amplifier to transfer electricalenergy from an input source of the power stage to the load and disablethe plurality of switches from transferring electrical energy from theinput source to the load; and in a second mode of operation of the powerstage, sequentially enable the linear amplifier in accordance with aprobability which is a function of the output voltage to transferelectrical energy from the input source of the power stage to the loadand sequentially apply switch configurations from the plurality ofswitch configurations to selectively activate or deactivate each of theplurality of switches in order to transfer electrical energy from theinput source of the power stage to the load.
 2. The power stage of claim1, wherein the controller is configured to operate the power stage inthe first mode of operation when a magnitude of the output voltage isbelow a threshold voltage and operate the power stage in the second modeof operation when the magnitude of the output voltage is above thethreshold voltage.
 3. The power stage of claim 1, wherein the controlleris further configured to, in a third mode of operation of the powerstage, disable the linear amplifier from transferring electrical energyfrom an input source of the power stage to the load and sequentiallyapply switch configurations from the plurality of switch configurationsto selectively activate or deactivate each of the plurality of switchesin order to transfer electrical energy from the input source of thepower stage to the load.
 4. The power stage of claim 3, wherein thecontroller is configured to operate the power stage in the first mode ofoperation when a magnitude of the output voltage is below a firstthreshold voltage, operate the power stage in the second mode ofoperation when the magnitude of the output voltage is above the firstthreshold voltage and below a second threshold voltage, and operate thepower stage in a third mode of operation when the magnitude of theoutput voltage is above the third threshold voltage.
 5. The power stageof claim 1, wherein the linear amplifier comprises a quadrantdigital-to-analog converter.
 6. The power stage of claim 1, wherein thelinear amplifier comprises a hemispherical digital-to-analog converter.7. A power stage for producing an output voltage to a load, comprising:a power converter comprising: a plurality of switches arranged tosequentially operate in a plurality of switch configurations; and anoutput for producing the output voltage comprising a first outputterminal and a second output terminal, wherein a first switch of theplurality of switches is coupled to the first output terminal and asecond switch of the plurality of switches is coupled to the secondoutput terminal; a linear amplifier coupled to the output; and acontroller configured to: control the linear amplifier to transferelectrical energy from an input source of the power stage to the load inaccordance with one or more least significant bits of a digital inputsignal; and control the power converter in accordance with bits of thedigital input signal other than the one or more least significant bitsto sequentially apply switch configurations from the plurality of switchconfigurations to selectively activate or deactivate each of theplurality of switches in order to transfer electrical energy from theinput source of the power stage to the load.
 8. The power stage of claim7, wherein the linear amplifier comprises a quadrant digital-to-analogconverter.
 9. The power stage of claim 7, wherein the linear amplifiercomprises a hemispherical digital-to-analog converter.
 10. A method forproducing an output voltage to a load, comprising: in a power stagecomprising power converter having a plurality of switches arranged tosequentially operate in a plurality of switch configurations and anoutput for producing the output voltage comprising a first outputterminal and a second output terminal, wherein a first switch of theplurality of switches is coupled to the first output terminal and asecond switch of the plurality of switches is coupled to the secondoutput terminal: in a first mode of operation of the power stage, enablea linear amplifier to transfer electrical energy from an input source ofthe power stage to the load and disable the plurality of switches fromtransferring electrical energy from the input source to the load; and ina second mode of operation of the power stage, sequentially enable thelinear amplifier in accordance with a probability which is a function ofthe output voltage to transfer electrical energy from the input sourceof the power stage to the load and sequentially apply switchconfigurations from the plurality of switch configurations toselectively activate or deactivate each of the plurality of switches inorder to transfer electrical energy from the input source of the powerstage to the load.
 11. The method of claim 10, further comprisingoperating the power stage in the first mode of operation when amagnitude of the output voltage is below a threshold voltage andoperating the power stage in the second mode of operation when themagnitude of the output voltage is above the threshold voltage.
 12. Themethod of claim 10, further comprising, in a third mode of operation ofthe power stage, disable the linear amplifier from transferringelectrical energy from an input source of the power stage to the loadand sequentially apply switch configurations from the plurality ofswitch configurations to selectively activate or deactivate each of theplurality of switches in order to transfer electrical energy from theinput source of the power stage to the load.
 13. The method of claim 12,further comprising operating the power stage in the first mode ofoperation when a magnitude of the output voltage is below a firstthreshold voltage, operating the power stage in the second mode ofoperation when the magnitude of the output voltage is above the firstthreshold voltage and below a second threshold voltage, and operatingthe power stage in the third mode of operation when the magnitude of theoutput voltage is above the third threshold voltage.
 14. The method ofclaim 10, wherein the linear amplifier comprises a quadrantdigital-to-analog converter.
 15. The method of claim 10, wherein thelinear amplifier comprises a hemispherical digital-to-analog converter.16. A method for producing an output voltage to a load, comprising: in apower stage comprising power converter having a plurality of switchesarranged to sequentially operate in a plurality of switch configurationsand an output for producing the output voltage comprising a first outputterminal and a second output terminal, wherein a first switch of theplurality of switches is coupled to the first output terminal and asecond switch of the plurality of switches is coupled to the secondoutput terminal: controlling a linear amplifier to transfer electricalenergy from an input source of the power stage to the load in accordancewith one or more least significant bits of a digital input signal; andcontrolling the power converter in accordance with bits of the digitalinput signal other than the one or more least significant bits tosequentially apply switch configurations from the plurality of switchconfigurations to selectively activate or deactivate each of theplurality of switches in order to transfer electrical energy from theinput source of the power stage to the load.
 17. The method of claim 16,wherein the linear amplifier comprises a quadrant digital-to-analogconverter.
 18. The method of claim 16, wherein the linear amplifiercomprises a hemispherical digital-to-analog converter.